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iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 1/12 FEATURES o o o o o o o o o o o o o o Input voltage 8 to 36 Vdc Highly efficient down converter Switching transistor and free-wheeling diode integrated Adjustment of the regulator cut-off current with external resistor Integrated 100 kHz oscillator without external components Switching frequency above the audible range Two downstream linear regulators with 200 mA/25 mA output current Three different output voltage combinations of 3.3 V version available (see Block Diagram) Small residual ripple with low capacitances in the F range Fault message at overtemperature and undervoltage at current-limited open-collector output Shutdown of switching regulator at overtemperature Internal reference voltages ESD protection Low space requirement with SO8 resp. tiny DFN10 package APPLICATIONS o 5 V resp. 3.3 V supply e.g. from 24 V industrial network
PACKAGES
o Option: enhanced temperature range of -40 to 85 C
SO8 (optional with thermal pad)
DFN10
BLOCK DIAGRAM
VB (8...36 V) RVB 1 4.7F 8 VB 2 VBR VHL 3 LVH 220H CVH 4.7F
5 VH
VH SWITCHING CONVERTER WD WDA WDB WDC OSCILLATOR VCC 6
(200 mA)
VCC +5 V +3.3 V +3.3 V +5 V
VCCA +5 V +3.3 V +5 V +3.3 V
ERROR
1
NER
CVCC 4.7F TEMPERATURE VCC REGULATOR
UNDERVOLTAGE ERROR DETECTION VCCA 7
(25 mA)
iC-WD
GND 4
REFERENCE
VREF VCCA REGULATOR
CVCCA 1F
Pin numbers for SO8 package Copyright (c) 2007 iC-Haus http://www.ichaus.com
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 2/12 DESCRIPTION The device iC-WD is a monolithic switching regulator with two downstream 5 V resp. 3.3 V linear regulators. In view of the high efficiency of the down converter for an input voltage range of 8 to 36 V, the iC-WD family is well-suited for industrial applications which require a stabilised 5 V resp. 3.3 V power supply with minimal power dissipation and few components. Switching transistor, free-wheeling diode and oscillator are integrated, limiting the necessary external elements for the switching regulator to the inductor, the back-up capacitor and one resistor. This resistor determines the regulator's cut-off current and thus its efficiency in the particular application at hand. The downstream linear regulators feature a low residual ripple even with relatively small smoothing capacitors in the F range. The output voltages have an internal reference and are specified 5% in the entire operating and temperature range. The use of two mutually independent linear regulators makes it possible to isolate the voltage supply of sensitive analogue circuits or sensors from the supply for digital and driver devices. The chip temperature and the output voltages are monitored. A fault is signalled via the current-limited open-collector output NER, for example by an LED display or a logical link with other error signals from the system. In the event of overtemperature, the switching regulator is disabled to reduce the power dissipation of the chip.
PACKAGES SO8, SO8tp, DFN10 to JEDEC Standard PIN CONFIGURATION SO8, SO8tp (top view)
1 8
PIN FUNCTIONS No. Name Function
VB
NER
2
7
VBR
3
VCCA
6
VHL
4
VCC
5
GND
VH
1 2 3 4 5 6 7 8
NER VBR VHL GND VH VCC VCCA VB
Error Output Pin for shunt Pin for inductor Ground (reference voltage) Intermediate Voltage Output (200 mA) Output (25 mA) Supply Voltage
The Thermal Pad (optional) is to be connected to a Ground Plane on the PCB. PIN CONFIGURATION DFN10 (top view) PIN FUNCTIONS No. Name Function 1 2 3 4 5 6 7 8 9 10 NER n.c. VBR VHL GND GND VH VCC VCCA VB Error Output Pin for shunt Pin for inductor Ground (reference voltage) Ground (reference voltage) Intermediate Voltage Output (200 mA) Output (25 mA) Supply Voltage
iC-WD Code... ... ...yyww
1
10
2
9
3
iC-WDx
... ...yyww
8
4
7
5
6
The Thermal Pad is to be connected to a Ground Plane on the PCB. Orientation of the package label ( WDx ...yyww) may vary.
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 3/12 ABSOLUTE MAXIMUM RATINGS
Values beyond which damage may occur; device operation is not guaranteed. Item No. Symbol Parameter Supply Voltage Voltage at VBR Current in VHL Voltage at VH Current in VCC Current in VCCA Voltage at NER ESD Susceptibility at all pins Junction Temperature Storage Temperature HBM, 100 pF discharged through 1.5 k WDB, WDC -40 -40 Peak duration 50 s Conditions Min. -0.3 -0.3 -800 -0.3 -500 -100 -0.3 Max. 38 38 800 8 4 4 38 2 1.5 150 150 V V mA V mA mA V kV kV C C Unit
G001 VB G002 V(VBR) G003 I(VHL) G004 V(VH) G005 I(VCC) G006 I(VCCA) G007 V(NER) G008 Vd() G009 Tj G010 Ts
THERMAL DATA
Operating Conditions: VB = 8...36 V, LVH = 220 H, Ri(LVH ) < 2 , CVH = 4.7 F, RVB = 1 Item No. T01 Symbol Ta Parameter Operating Ambient Temperature Range (extended temperature range on request) Thermal Resistance Chip to Ambient Thermal Resistance Chip to Ambient Thermal Resistance Chip to Ambient SMD mounting on PCB, without additional cooling SMD mounting on PCB, with approx. 3 cm cooling surface (see Evaluation Board) SMD mounting on PCB, therm. pad soldered to approx. 2 cm cooling area 30 Conditions Min. -25 Typ. Max. 70 C Unit
T02 T03 T04
Rthja Rthja Rthja
170 100 60
K/W K/W K/W
All voltages are referenced to ground unless otherwise stated. All currents into the device pins are positive; all currents out of the device pins are negative.
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 4/12 ELECTRICAL CHARACTERISTICS
Operating Conditions: VB = 8...36 V, LVH = 220 H, Ri(LVH) < 2 , CVH = 4.7 F, RVB = 1 , Tj = -40...125 C, unless otherwise noted Item No. 001 Symbol Parameter Conditions Min. VB Permissible Supply Voltage Range I(VCC) = -200...0 mA; WD, WDC WDA, WDB 8 Typ. Max. 36 V Unit
Total Device
Linear Regulator VCC (200 mA) 101 VCCnom Output Voltage
4.75 3.135 -200 4.7
5.00 3.30
5.25 3.465 0
V V mA F mVss
102 103 104
I(VCC) CVCC VCCrip
Permissible Load Current Min. Output Capacity for Stability Residual Ripple Evaluation Board (see Fig. 8), Tj = 27 C: I(VCC) = -200 mA, I(VCCA) = -20 mA I(VCCA) = -25...0 mA; WD, WDB WDA, WDC
35
Linear Regulator VCCA (25 mA) 201 VCCAnom Output Voltage
4.75 3.135 -25 1
5.00 3.30
5.25 3.465 0
V V mA F mVss
202 203 204
I(VCCA) CVCCA VCCArip
Permissible Load Current Min. Output Capacity for Stability Residual Ripple Evaluation Board (see Fig. 8), Tj = 27 C: I(VCC) = -200 mA, I(VCCA) = -20 mA I(VCC) = 0, I(VCCA) = 0, Tj = 25 C; VB = 12 V VB = 24 V VB = 30 V I(VCC) + I(VCCA) = -100 mA, Tj = 25 C, WD, WDB, WDC; VB = 12 V VB = 24 V VB = 30 V I(VCC) + I(VCCA) = -100 mA, Tj = 25 C, WDA; VB = 12 V VB = 24 V VB = 30 V I(VCC) + I(VCCA) = -200 mA, Tj = 25 C, WD, WDB, WDC; VB = 12 V VB = 24 V VB = 30 V I(VCC) + I(VCCA) = -200 mA, Tj = 25 C, WDA; VB = 12 V VB = 24 V VB = 30 V
30
Switching Regulator VB, VBR, VHL, VH 301 I0(VB) Quiescent Current in VB
4.5 3.0 2.5
mA mA mA
302
I(VB)
Current in VB with partial load
72 37 30 61 33 24
mA mA mA mA mA mA
303
I(VB)
Current in VB with partial load
304
I(VB)
Current in VB with full load
132 69 55 116 62 43 4.7 12 20 60 90 7.5 7 5.8 5.4 6 6.3 120
mA mA mA mA mA mA F kHz kHz kHz V V V V V V
305
I(VB)
Current in VB with full load
306 307 308 309 310
CVH R(CVH ) f0(VHL) fl(VHL) V0(VH)
Charging Capacitor at VH Series Resistance of CVH for stability Switching Frequency with no load I(VCC) = 0, I(VCCA) = 0 Switching Frequency with load No-load Voltage VH I(VCC) + I(VCCA) = -200 mA Tj = 27 C WD, WDB, WDC; I(VCC) = 0, I(VCCA) = 0, VB = 36 V Tj = 27 C WDA; I(VCC) = 0, I(VCCA) = 0, VB = 36 V Tj = 27 C WD, WDB, WDC; I(VCC) + I(VCCA) = -200 mA, VB = 8 V Tj = 27 C
311
V0(VH)
No-load Voltage VH
312
Vl(VH)
Voltage VH with load
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 5/12 ELECTRICAL CHARACTERISTICS
Operating Conditions: VB = 8...36 V, LVH = 220 H, Ri(LVH) < 2 , CVH = 4.7 F, RVB = 1 , Tj = -40...125 C, unless otherwise noted Item No. 313 Symbol Vl(VH) Parameter Voltage VH with load Conditions Min. WDA; I(VCC) + I(VCCA) = -200 mA, VB = 8 V Tj = 27 C VH < Vl(VH), RVB = 1 4.5 5.0 -500 130 3 8 12 -460 -400 150 15 16 Typ. Max. V V mA C C % Unit
314 401 402 403
Ioff Toff Thys VCC VCCA VCChys VCCAhys Vs(NER) Isc(NER)
Max. Cut-off Current in VHL Thermal Shutdown Threshold Thermal Shutdown Hysteresis Relative Undervoltage Threshold at VCC, VCCA referenced to VCCnom , VCCAnom Undervoltage Hysteresis referenced to VCCnom , VCCAnom Saturation Voltage lo at NER Short-Circuit Current lo in NER
Error Detection NER
404 405 406
2 I(NER) = 5 mA V(NER) = 1...36 V Tj = -40 C Tj = 27 C Tj = 70 C Tj = 125 C NER = off, V(NER) = 0...36 V 5
4
7 0.7 21
% V mA mA mA mA mA A
15 12 10 8 0 10
407
I0(NER)
Collector Off-State Current in NER
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 6/12 DESCRIPTION OF FUNCTIONS Fig. 1 illustrates the operating principle of the switching converter in simplified form. When the switch S closes in steady-state condition, a linearly increasing charging current for the capacitor CVH flows through the coil LVH in addition to the load current in RL . The energy from the supply VB is stored in the coil's magnetic field. When the switch opens, the current flows via the diode through the coil; its energy content is supplied to capacitor and load.
Vsat VB S V(LVH) LVH VH
100mV
cillator frequency is reduced as the level of voltage VH rises (Fig. 5).
500mV
400mV
VR = VB - VBR
300mV
200mV typ.
VD
CVH
RL
0V 5.5V 6.0V 6.5V 7.0V VH 7.5V
Figure 2: Regulating characteristic VR = f (VH) Figure 1: Principle of operation
1.5V
The block diagram on page 1 shows the iC-WD with typical wiring. The internally generated clock pulse closes the switch between VBR and VHL and the current in the coil rises (charging phase). A control variable, VR in accordance with the regulating characteristic in Fig. 2, is obtained from the voltage VH and the internal reference voltage and is compared to the voltage at shunt RVB . When the cut-off current Ioff = VR /RVB is reached, the switch opens and the coil current runs free via the integrated power diode (discharge phase). When the next clock signal occurs, this charging and discharging process is repeated. Fig. 6 shows the resulting current and voltage characteristics. The current rise (tr ) and fall times (tf ) depend on the voltage VH at the inductor. The following approximation applies: Ioff tr = LVH VB - Vsat - VH Ioff tf = LVH VH + VD (1)
max.
1.0V Vsat = VB - VHL
typ.
0.5V
0V 0A 100mA 200mA 300mA 400mA I(VHL) 500mA
Figure 3: Saturation voltage of switching transistor
1.5V
max.
1.0V VD = - VHL
Vsat = VB - VHL: Saturation voltage of the switching transistor plus voltage drop at RVB VD : Forward voltage of the free-wheeling diode The current dependencies of the saturation and diode forward voltage (Fig. 3 and 4) are ignored here, as are the losses due to the internal resistance of the coil. The regulator operates at a constant frequency under load. To prevent VH from rising without load, the os-
typ.
0.5V
0V 0A
100mA
200mA
300mA
400mA I(VHL)
500mA
Figure 4: Forward voltage of free-wheeling diode
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 7/12
125kHz
typ. 100kHz
ing mode. Since both the charging and the discharging current flow in VH, the initial approximation of the mean current-carrying capacity of VH is: IL (VH) = 1 tr + tf I 2 off T (2)
75kHz fosz 50kHz 25kHz
T = 1/fosz : Period of internal oscillator (Fig. 5)
5.5V 6.0V 6.5V 7.0V 7.5V
0 VH
Figure 5: Oscillator Frequency The following three operating states of the regulator are described as a function of the supply voltage and the load current:
For load current IL at output VH, the iC-WD adjusts the cut-off current Ioff to the following value (VB > VH + Vsat ):
Ioff =
2 * IL (VH)
T LVH
1
1 VB-Vsat -VH 1 + VH+V
D
(3)
Ioff
I(LVH)
Since only during the charging phase current is drawn from supply voltage VB, the mean current consumption is: (VB > VH + Vsat ): I(VB) = Ioff tr + I0 (VB) T (4)
0 VB
I0 (VB): current consumption without load at VCC, VCCA (no-load operation)
VHL
VH
0
tr
tf T = 1/f osz
Figure 6: Intermittent flow SWITCHING REGULATOR: Intermittent flow When charging and discharging operation are concluded within a single clock pulse period (tr + tf < T ) and the coil current drops to zero, intermittent flow prevails (Fig. 6). This is the case when the supply voltage is sufficiently high or the load current sufficiently low. The current-carrying capacity and power consumption of the regulator can be easily specified for this operat-
SWITCHING REGULATOR: Continuous flow If the inductor receives recharge with the next clock signal before the coil current has run free, no gap is created in the current. Such continuous flow (Fig. 7) occurs when the supply voltage is too low or the load current too high. Since the charging process begins at various current levels not equal to zero, the timing and the required cut-off current are difficult to express. In general, fluctuations occur in the clock frequency at the time constants of the charging and discharging phase, which in turn depend on the of supply voltage and the load current. Since no current gap occurs, the cut-off current may be lower than during intermittent flow (at the same load). The losses in the switching transistor, in the free-wheeling diode and due to the internal resistance of the inductor are consequently lower; the efficiency of the regulator is thus higher. In addition, interference due to the internal resistance of supply voltage source and standby capacitor CVH is lower. Depending on the model and quality of the coil, however, the low frequent fluctuations may be audible.
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 8/12
Ioff
VH to VCC or VCCA the size of standby capacitor CVH should be increased for this type of operation (e.g. 22 F). SERIES REGULATORS VCC and VCCA To obtain the lowest possible interference voltage even with the small smoothing capacitor CVH , two independent series regulators with a NPN emitter follower stage are connected downstream of intermediate voltage VH. The Output voltages VCC or VCCA are constant 5%. The suppression of interference voltage for the output voltages is best when VH is also no lower than 6.0 V dynamically (iC-WDA: 4.3 V). The series regulators are compensated internally, hence they are stable during no-load operation, without external capacitance. Stability over the entire load range is ensured by the minimum capacitance values for CVCC and CVCCA given in the electrical characteristics. Current-limited outputs are used as protection against destruction in the event of a short circuit. FAULT EVALUATION The two output voltages VCC and VCCA are monitored. When the voltage drops below the undervoltage threshold (due to overload, etc.), a message is sent to the current-limited open-collector output NER (active low). The chip temperature is also monitored. In the event of overtemperature the switching regulator is turned off and it is not enabled against until the chip temperature has decreased. This thermal shutdown of the regulator is indicated by NER = low. Since the fault output NER is current-limited, an LED can be connected directly for the optical message display, however the additional power dissipation which occurs
VB
VH
VHL 0
I(LVH) 0
tr T = 1/f osz
Figure 7: Continous flow SWITCHING REGULATOR: Operation at low supply voltage A third operating state occurs when the supply voltage VB is scarcely higher than VH. The cut-off current can no longer be reached in this case since: (VB - VH - Vsat )/RLVH < Ioff . The switching transistor is switched on continuously and VH reaches: VH = VB - Vsat - I(VH) x RLVH . Factoring in this special feature makes it possible to operate the iC-WD even at low supply voltage. Operability is still guaranteed at VB 7.6 V. Nonetheless, the maximum currentcarrying capacity depends on the coil's internal resistance and supply voltage VB. The transition from regulator mode to continuously activated transistor is fluid. To avoid feedback of interference voltage from
Pv = I(NER) x (VB - Vfw (LED))
(5)
must be taken into account. A resistor RLED in series with the LED can reduce the additional chip power dissipation in the event of a fault. CMOS- or TTLcompatible logic inputs can be activated with a pull-up resistor at NER.
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 9/12 APPLICATIONS INFORMATION DIMENSIONING The size of shunt RVB determines the cut-off current Ioff . By varying this in combination with the value for the inductor LVH , the power input, the efficiency and the timing can be adapted to the application. Normally the supply voltage range and the maximum output current for VCC and VCCA is specified. Define whether or not only intermittent flow is desired. The maximum inductance LVH can be estimated on the following basis: In the worst situation, charging and discharging process last exactly one period, which is the case at minimum supply power. The cut-off current adjusts to Ioff = 2 x ILmax (VH). From equation (1) it follows that: LVHmax = Tmin x 2ILmax (VH) 1
1 VBmin -Vsat -VH 1 + VH+V
Using equation (3) it is possible to determine the maximum cut-off current for intermittent flow. The maximum value for VB must be inserted:
Ioffmax =
2 * ILmax (VH)
Tmax * LVH
1
1 VBmax -Vsat -VH 1 + VH+V
D
The shunt RVB can be dimensioned with this information. VRmax can be obtained from Fig. 2:
RVB =
D
VRmax Ioffmax
EXAMPLE Specified are: VB = 18...36 V, ILmax = 100 mA; the maximum inductance can be estimated to: 1/125 kHz * 200 mA 1
1 18 V -1.1 V -7.0 V 1 + 7.0 V +1.1 V
LVHmax =
= 178 H
The inductance selected is 150 H, for example. Consequently, the maximum required cut-off current and the shunt are found to be: 1/75 kHz * 150 H 1
1 30 V -1.1 V -7 V 1 + 7 V +1.1 V
Ioffmax =
2 * 100 mA
= 324 mA
RVB =
400 mV 1.2 324 mA = 220 H, RVB = 1 is suitable for maximum performance throughout the entire specification range.
It is not always possible to dimension the circuit for intermittent flow, particularly not when high output currents are required with a low supply voltage. Permitting continuous flow may prove conducive to higher efficiency and less interference. The inductance selected is to be higher than in the above formula; the equations for maximum cut-off current and the shunt can be used with the selected coil. It is simplest to ascertain the correct dimensioning by experiment in a test set-up (Evaluation Board). The dimensioning shown in the block diagram (LVH
SELECTING THE COMPONENTS Since the coil must not to become saturated, it should be designed for maximum cut-off current. This can be checked by testing the coil current with a current probe: In the event of saturation the current rises much more sharply than with low currents. A low internal resistance of the coil reduces the losses and increases the regulator's efficiency. When the supply voltage is low,
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 10/12 this internal resistance can determine the maximum available output current (equation 4). The EMI (electromagnetic interference) caused by the coil should be taken into account. Toroidal core coils have little noise radiation but are expensive and difficult to install. Bar cores are reasonably priced and easy to handle but emit higher radiation. Reasonably priced RF chokes in the range of a few tens to a few hundreds H are suitable for modest EMI requirements. Additional interference may be caused by decaying of the voltage at VHL when the coil current drops to zero (Fig. 6). Parasitic capacitances at VHL form an oscillating circuit with the coil. This undesirable oscillating circuit can be damped to an uncritical magnitude by installing a resistor (> 10 k) parallel to the coil. The selection of the backup capacitor CVH is unproblematic. Due to the series regulators, the ripple of the intermediate voltage VH does not affect the output voltages VCC and VCCA. Therefore a low capacitance level without special demands on the internal resistance is sufficient. A combination of electrolytic and ceramic capacitor (e.g. 4.7 F/100 nF) is recommended. Tantalum capacitors are also possible when they are allowed to operate at AC amplitudes like the residual ripple of voltage VH. The stability of the series regulators is guaranteed for the entire load range when the values for CVCC and CVCCA given in the electrical characteristics are selected. The suppression of interference voltage is improved by small capacitor series resistors. The combination of tantalum and ceramic capacitors is also recommended in this case. If one of the two outputs remains open, its capacitor can be omitted. To avoid feedback of interference from supply voltage VB onto output voltages VCC and VCCA, provide blocking directly at pin VB. A combination of tantalum and ceramic capacitors is also recommended in this case (several F/100 nF). PRINTED CIRCUIT BOARD LAYOUT The GND path from the switching regulator and from each series regulator should be strictly separated to avoid cross couplings. The neutral point of all GND conductors is the GND connection at the iC-WD. It is possible and not critical, however, to route the GND of the supply VB and the base point of capacitor CVH together to the neutral point. The capacitor CVH should be very close to the pin VH however. To keep down the decay at the open end of the coil (pin VHL), the capacitance of this connection should be low, that means the connection should be short. The blocking capacitors of supply voltage VB are to be placed as close as possible to pins VB and GND. The capacitors for the outputs VCC and VCCA should be placed directly by the load and not directly by the iC to also block interferences which are coupled via the wiring to the load. A ground plane should be cut out underneath the wiring of CVCC and CVCCA . The printed circuit conductor between VB, the shunt RVB, and VBR should have a low impedance, since voltage drops in the supply path change the effective size of the shunt and reduce the maximum cut-off current. The Thermal Pad (optional with the SO8) should be connected to an appropriate copper area on the PCB. It has proven to be advantageous to use thermal vias directly underneath the iC to transfer the power dissipation to a different layer, e.g. a ground plane.
e.g.: Siemens Matsushita B78108-S1224-J (220 H/250 mA, axial leads), TDK series NLC565050T-. . . (SMD), TOKO series 10RF459-. . . (SMD shielded)
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 11/12 EVALUATION BOARD For the iC-WD devices an Evaluation Board is available for test purpose. The following figures show
RVB VB CVB 4.7 F GND RNER 1.2 k 8 VB 1 2 VBR VHL 3 220 H CVH 4.7 F 5 VH
the schematic as well as the layout of the Evaluation Board.
LVH VH
SWITCHING REGULATOR VH
DNER LED OSCILLATOR VCC 6 VCC CVCC NER 1 NER THERMAL SHUTDOWN 4.7 F REG VCC GND
LOW VOLTAGE ERROR DETECTION
VCCA
7
VCCA CVCCA 1 F
iC-WD
GND 4
REFERENCE
VREF REG VCCA
GND
Figure 8: Schematic diagram of the Evaluation Board
Figure 9: Evaluation Board (components side)
This specification is for a newly developed product. iC-Haus therefore reserves the right to change or update, without notice, any information contained herein, design and specification; and to discontinue or limit production or distribution of any product versions. Please contact iC-Haus to ascertain the current data. Copying - even as an excerpt - is only permitted with iC-Haus approval in writing and precise reference to source. iC-Haus does not warrant the accuracy, completeness or timeliness of the specification on this site and does not assume liability for any errors or omissions in the materials. The data specified is intended solely for the purpose of product description. No representations or warranties, either express or implied, of merchantability, fitness for a particular purpose or of any other nature are made hereunder with respect to information/specification or the products to which information refers and no guarantee with respect to compliance to the intended use is given. In particular, this also applies to the stated possible applications or areas of applications of the product. iC-Haus conveys no patent, copyright, mask work right or other trade mark right to this product. iC-Haus assumes no liability for any patent and/or other trade mark rights of a third party resulting from processing or handling of the product and/or any other use of the product.
iC-WD A/B/C
SWITCHED-MODE DUAL VOLTAGE REGULATOR
Rev D1, Page 12/12 ORDERING INFORMATION
Typ iC-WD
(VCC/VCCA) (5/5 V)
Package SO8 SO8 thermal pad DFN10 (on request) DFN10 DFN10 DFN10 -
Order Designation iC-WD SO8 iC-WD SO8-TP iC-WD DFN10 iC-WD EVAL WD2D iC-WDA DFN10 iC-WDA EVAL WD2D iC-WDB DFN10 iC-WDB EVAL WD2D iC-WDC DFN10 iC-WDC EVAL WD2D
Evaluation Board iC-WD iC-WDA (3.3/3.3 V)
Evaluation Board iC-WDA iC-WDB (3.3/5 V)
Evaluation Board iC-WDB iC-WDC (5/3.3 V)
Evaluation Board iC-WDC
For technical support, information about prices and terms of delivery please contact: iC-Haus GmbH Am Kuemmerling 18 D-55294 Bodenheim GERMANY Tel.: +49 (61 35) 92 92-0 Fax: +49 (61 35) 92 92-192 Web: http://www.ichaus.com E-Mail: sales@ichaus.com
Appointed local distributors: http://www.ichaus.de/support_distributors.php

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